Low power dynamic logic gate with full voltage swing operation

ABSTRACT

Dynamic low-power logic using recycled energy is disclosed. Logic circuits have a discharge path, a precharge path and a control circuit. The precharge path is a PMOS transistor coupled between the clock line and the output node of the circuit and configured to charge the output node to the logic high voltage of the clock line during a precharge phase. During an evaluation phase, the discharge path computes the desired logic function at the output node. A control circuit is connected between the output node and the clock line and to the gate of the precharge path transistor. The control circuit provides the proper gate drive, regardless of the voltage on the output node or the inputs to the discharge path, to guarantee that the precharge transistor fully charges the output node to the logic high voltage of the clock line, which provides recycled energy for operating the circuit.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is related to U.S. patent application Ser. No.09/967,189, entitled, RESONANT LOGIC AND THE IMPLEMENTATION OF LOW POWERDIGITAL INTEGRATED CIRCUITS, filed Sep. 27, 2001, now U.S. Pat. No.6,559,681, incorporated by reference, and U.S. patent application Ser.No. 09/614,494, entitled, RESONANT LOGIC AND THE IMPLEMENTATION OF LOWPOWER DIGITAL INTEGRATED CIRCUITS, filed Jul. 11, 2000, now U.S. Pat.No. 6,448,916. This application is a continuation of U.S. patentapplication Ser. No. 10/087,604, filed Mar. 1, 2002, entitled LOW POWERDYNAMIC LOGIC GATE WITH FULL VOLTAGE SWING OPERATION, now U.S. Pat. No.6,552,574.

FIELD OF THE INVENTION

This invention is related generally to reduced power logic and morespecifically to reduced power logic having full voltage output swing andoperating with recycled energy.

DESCRIPTION OF THE RELATED ART

A previous application, U.S. patent application Ser. No. 09/967,189,entitled RESONANT LOGIC AND THE IMPLEMENTATION OF LOW POWER DIGITALINTEGRATED CIRCUITS, disclosed a logic system operating with recycledenergy. The logic disclosed therein included several logic gates eachhaving a discharge path 10 and a precharge path 12 as shown in FIG. 1.The discharge path 10 and precharge path 12 are connected in parallelbetween a clock line 14 and an output node 16, having load capacitance,C_(L) 18. The discharge path 10 is generally a logic circuit stage thatimplements a logic function, such as an inverter gate, NAND gate, asshown in FIG. 2A, or NOR gate (not shown), or part of a more complexlogic function. A conductive path is developed between the output nodeand the clock line depending on the state of one or more inputs to thelogic circuit stage during an evaluation period or phase. Thus, thedischarge path 10 is conditionally conductive.

The precharge path 12, also connected between the output node 16 and theclock line 14, develops a conductive path, unconditionally, during aprecharge phase or period. During this phase, the output node 16 isprecharged to a voltage level related to the voltage level achieved bythe clock line, which is a logic high during the precharge phase.

During the evaluation phase, the precharge path 12 is not conductive andduring the precharge phase, the discharge path 10 is not conductive.Thus, in operation after the output node 16 is charged during theprecharge phase, the logic function is evaluated during the evaluationphase, using the charge on the output node 16. If the inputs are suchthat the logic circuit stage is not conductive, then the output node 16stays charged at the voltage level to which it was precharged. If theinputs are such that the logic circuit stage is conductive, then theoutput node 16 is discharged to approximately the low potential of theclock signal 14.

In the previous application, the precharge path 12 is implemented as adiode, as shown in FIG. 2B. The diode implementation however creates aproblem, in that the output node 16 cannot be precharged to a voltagesubstantially equal to the high voltage of the clock signal 14. Thislimits the voltage output of the output node 16 and has effects oncircuitry that receives the less-than-full swing output from the logiccircuit stage. One such effect is reduced drive to subsequent logicinputs if the circuit is operated at high clock rates, thereby reducingthe maximum clock rate of such circuitry.

Therefore, there is a need the output of the logic circuit stage toachieve voltage levels substantially equal to the voltage levels of theclock signal carried on the clock line to which the logic circuit stageis connected.

BRIEF SUMMARY OF THE INVENTION

The present invention is directed towards the above need. The presentinvention, in accordance with one embodiment of the present invention,includes a discharge path, a precharge path and a control circuit. Thedischarge path is connected between a clock line and an output node andincludes one or more transistors configured to evaluate a logic functionof at least one input during an evaluation phase. The precharge path isconnected between the clock line and the output node, and includes aPMOS transistor having a gate and a channel between a source and drainregion of the transistor, the drain being connected to the output nodeand the source being connected to the clock line. The control circuithas an output connected to the gate of the precharge path transistor andis configured to maintain a source-to-gate voltage on the precharge pathtransistor such that, independent of the states of the inputs and theoutput node, the channel of the precharge transistor provides aconductive path between the clock line during a precharge phase.

The clock line of the present invention is connected to a clock circuitthat captures, on the clock line, energy from the output node via thedischarge path and provides a portion of the captured energy back to theoutput node via the precharge path.

A method in accordance with one embodiment of the present inventionincludes the steps of disabling the precharge path during a firstvoltage of the clock signal by providing the first voltage to the sourceof the PMOS transistor and enabling the precharge path during a secondvoltage of the clock signal by providing the second voltage to thesource of the PMOS transistor and providing to a gate of the PMOStransistor a voltage having a range of approximately a NMOS transistorthreshold voltage above the first voltage of the clock line to one PMOStransistor threshold voltage below the second voltage of the clock line.

An advantage of the present invention is that the voltage range of theoutput node is approximately equal to the voltage range of the clockline, which is approximately a range from zero volts to the positivesupply voltage.

Another advantage is that the output node can drive more logic inputs ata given clock cycle rate.

Yet another advantage is that the logic circuitry can operate at ahigher clock cycle rate.

Yet another advantage is that lower power operation is achieved byremoving a direct path between the output node and the clock line thatconsumes power during switching.

Yet another advantage is that low power operation is achieved because aportion of the energy used to precharge the output node and operate thedischarge path is returned to the output node by the clock circuit.

BRIEF DESCRIPTION OF THE DRAWINGS

These and other features, aspects and advantages of the presentinvention will become better understood with regard to the followingdescription, appended claims, and accompanying drawings where:

FIG. 1 shows the precharge and discharge paths disclosed in a previousapplication;

FIG. 2A shows a logic circuit stage for a NAND gate;

FIG. 2B shows a diode implementation of the precharge path;

FIG. 3 shows a block diagram the discharge, precharge path and controlcircuit of the present invention;

FIG. 4A shows an embodiment of the control circuit of the presentinvention;

FIG. 4B show an embodiment of the precharge path of the presentinvention;

FIG. 5 shows an INVERTER gate, in accordance with the present invention;

FIG. 6 shows a NAND gate, in accordance with the present invention;

FIG. 7 shows a NOR gate, in accordance with the present invention;

FIG. 8 shows waveforms depicting the operation of an inverter, inaccordance with the present invention;

FIG. 9 shows a NAND gate with adjustable drive capability, in accordancewith the present invention;

FIG. 10 shows a NAND gate with reduced charge sharing effect;

FIG. 11 shows an INVERTER with reduced charge-pump effect;

FIG. 12 shows how a circuit of the present invention interfaces withconventional logic gates;

FIG. 13 shows a clock circuit block diagram that provides a clock signalto the logic circuitry of the present invention; and

FIG. 14 shows an embodiment of the clock circuit block diagram.

DETAILED DESCRIPTION OF THE INVENTION

FIG. 3 shows a block diagram of the discharge path 10, precharge path 30and control circuit 32 of the present invention. The precharge path 30of the present invention is connected between the output node 16 and theclock line 14 and to a control circuit 32 via path y3. The controlcircuit 32 is configured to substantially reduce the voltage drop acrossthe precharge path 30 during precharging.

FIG. 4A shows an embodiment of the control circuit 32 of the presentinvention and FIG. 4B shows an embodiment of the precharge path 30 ofthe present invention. The diode of the previous precharge path isreplaced with a transistor 40, whose channel is connected between theoutput node 16 and the clock line 14. The gate node y3 of the prechargetransistor 40 is connected to the control circuit 32 node y3 whichprovides the proper source-to-gate voltage to turn on the transistor 40regardless of whether the output node 16 is charged to a logic high or alogic low. Capacitance Cb is an intrinsic capacitance between the y1 andy3 nodes.

FIG. 5 shows an INVERTER gate, in accordance with one embodiment of thepresent invention. Transistor 46 provides the discharge path andimplements an inverter logic function. Transistor 46 has its channelconnected between the output node 16 and the clock line 14. The gate oftransistor 46 is connected to an input 48 on which the transistor 46operates to produce an inverted version of the input 48 at the outputnode 16. The substrate of transistor 46 is tied to the lowest voltage inthe circuit, Vss. The control circuit 32 includes transistor 42, an NMOStransistor, and transistor 44 a PMOS transistor, each connected in adiode configuration. The channels of transistor 42 and transistor 44 areeach connected between the gate of transistor 40 and the output node 16and the sources of both transistors 42, 44 connect to the output node16. The substrate of the NMOS transistor 42 is connected to Vss and thesubstrate of PMOS transistor is connected to Vdd. Transistor 40, theprecharge PMOS transistor, has its channel connected between the clockline 14 and the output node 16, the source of transistor 40 beingconnected to the clock line 14 and the drain of transistor 40 beingconnected to the output node 16. The substrate of transistor 40 isconnected to Vdd.

The clock line 14 carries a clock signal that has a first voltage and asecond voltage. If the clock signal is a digital signal, the firstvoltage is a logic high and the second voltage is a logic low. During aprecharge phase, while the clock signal is at a logic high, the outputnode 16 is precharged through transistor 40, whose channel is madeconductive by either transistor 44 or transistor 42. During anevaluation phase, while the clock signal is at a logic low, transistor40 is rendered non-conductive and transistor 46 is conditionallyconductive depending on whether the input 48 is high or low. If theinput 48 is high, then transistor 46 is conductive, thereby dischargingthe output node 16 to the clock line 14. If the input 48 is low, thentransistor 46 is not conductive and the output node 16 is maintained ator near the voltage to which it was previously precharged.

As is apparent from the above description, output node 16 of theINVERTER circuit 38 has a voltage that is either close to the lowervoltage on the clock line or close to the higher voltage on the clockline. Transistor 42 handles the case in which the voltage on the outputnode 16 is close to the lower voltage on the clock line 14, at the startof the precharge phase. Transistor 44 handles the case in which thevoltage on the output node 16 is close to the higher voltage one clockline 14, at the start of the precharge phase.

If the voltage on the output node 16 is close to the lower voltage onthe clock line, i.e., close to zero volts, at the start of the prechargephase, and the voltage on the clock line 14 during the precharge phaseis a logic high, approximately equal to the positive supply voltage,then the channel of transistor 40 becomes conductive, because there issufficient source-to-gate voltage Vsg, which is taken as positive in thedirection of source to gate. The source node of transistor 40 is at alogic high, and the gate is approximately one threshold voltage, Vtn,above the voltage at the output node, i.e., Vout+Vtn, where Vtn is thethreshold voltage for an NMOS transistor. For example, if the outputnode 16 is zero volts, then the voltage on the gate of 40 isapproximately a threshold voltage Vtn for an n-channel device, because44 is a diode-connected transistor. If, in one embodiment, Vtn for anNMOS transistor and Vtp are each about one volt, then the gate of 40 isapproximately 1 volt. If, in this embodiment, the positive supplyvoltage is 5 volts, then the source-to-gate voltage for the PMOStransistor 40 is about +4 volts, which is greater than the thresholdvoltage Vtp. Thus, under the above conditions, transistor 40 has aconducting channel between the clock line 14 and the output node 16.This conducting channel allows the output node 16 to charge from clockline 14. As the output node rises towards the logic high voltage of theclock line 14, the channel of transistor 42 becomes less conductive andcuts off at the point when the output voltage is approximately ann-channel threshold voltage Vtn higher than the gate of 40. At thisvoltage, transistor 44 begins to help maintain the source-to-gate Vsgdrive of transistor 40, by holding the gate voltage of transistor 40 atapproximately Vtp below the output voltage Vout, i.e., at Vout−Vtp.Thus, transistor 44 helps to assure that the gate of transistor 40cannot rise so far as to diminish the transistor 40's source-to-gatevoltage, approximately Vout−Vtp, that is necessary for maintainingconduction of transistor 40.

It should be noted that if the output node 16 is charged to the logichigh voltage of the clock line 14, then channel of transistor 46 cannotconduct during the precharge phase because there is insufficientgate-to-source voltage, no matter which terminal of transistor 46 isconsidered the source node and regardless of the state of the input 48to transistor 46.

During the evaluation phase, transistor 40 is non-conducting regardlessof the state of the output node 16. If the state of the output nodestays charged during the evaluation phase, because the logic path isnon-conducting, the drain-to-gate voltage Vdg of transistor 40 isV′out−Vg, where V′out is close to, but slightly less than, the logichigh voltage of the clock line, and Vg is the gate voltage from theprevious precharge cycle. Though the source terminal of transistor 40has a voltage of approximately zero volts, the voltage Vdg=V′out−Vgbetween the drain and gate of transistor 40 is not sufficient to causetransistor 40 to conduct from output 16 to clock line 14, because it isless than the threshold voltage Vtp of transistor 40, i.e.,Vdg=Vtp−(Vout−V′out), and V′out is slightly less than Vout.

If the output node was previously discharged, then the gate oftransistor 40 is at approximately Vout+Vtn, where Vout is close to thelogic low voltage of the clock line 14, and both the source-to-gatevoltage and drain-to-gate voltage for transistor 40 have the incorrectpolarity for conduction between the clock line 14 and the output node16.

Thus, the device of FIG. 5 has an output voltage on the output node 16that is either substantially close to the logic high voltage or a logiclow voltage of the clock line 14. If the clock line 14 has a low voltageof zero volts and a high voltage equal to the positive supply voltage,then the output voltage of the circuit of FIG. 5 has a full logic swing.

Compared to a traditional logic inverter, the circuit 38 of FIG. 5 hasthe advantages of low power and high drive capability. The low powercharacteristic derives from not using a PMOS and an NMOS transistor inseries between the positive supply voltage and ground. In the latterarrangement, a high current flows during switching because there is ashort time interval in which both the PMOS and NMOS transistors are on.Not only does this causes a high current to flow from the positivevoltage supply to ground, but it also causes a the PMOS and NMOStransistors to contend with each other during the charging ordischarging of the load capacitance at the output of the traditionalinverter. In contrast, the inverter of the present invention, hasseparate control signals for NMOS and PMOS transistors. High switchingcurrents are avoided and there is no contention at the output.Controlling the gate voltage and size of transistor 40 allows the outputto drive large capacitive loads. The total area of the circuit of FIG. 5can be made to be smaller than a traditional device having the samedrive characteristics.

FIG. 6 shows a NAND gate 54, in accordance with the present invention,and FIG. 7 shows a NOR gate 56, in accordance with the presentinvention. The discharge path 10 of FIG. 6 includes two or more NMOStransistors 58-60, connected in series to implement a multi-input NANDfunction during the evaluation phase. The discharge path 10 of FIG. 7includes two or more NMOS 62-64 transistors connected in parallel toimplement a multi-input NOR function during the evaluation phase.

FIG. 8 shows waveforms depicting the operation of an inverter 38 of FIG.5, in accordance with the present invention. The low phase of the clock14 is the evaluation phase and the high phase of the clock is theprecharge phase. The output 16 follows the waveform on the clock line 14when the input to the inverter is high, causing the output 16 to be lowduring the evaluation phase. The output voltage is maintained at thepositive supply voltage, Vdd, when the input is low. The clock waveformon clock line 14 is not limited to a square wave. Sinusoidal waveformscan also be used for the clock signal. The precharge and evaluationtimes for a sinusoidal waveform are determined by the thresholds of thetransistors comprising the inverter 38. FIG. 8 shows the output inaccordance with the present invention, i.e., without the Vt drop thatwould have been present otherwise.

FIG. 9 shows a NAND gate 70 with adjustable drive capability, inaccordance with the present invention. The control circuit of FIG. 5 ismodified, removing the NMOS diode-connected transistor 42 and adding anauxiliary NAND function between the gate of transistor 40 and the clockline 14. The auxiliary NAND function includes two NMOS transistors 72,74 whose channels are connected in series and whose gates are eachconnected to one of the inputs 76, 78 of the discharge path logicfunction. If and when the output node 16 of the circuit is discharged bythe discharge path during the evaluation phase, the gate of transistor40 is also discharged to the logic low voltage of the clock line 14,because transistor 72 and transistor 74 are conductive. This increasesthe gate drive of transistor 40 when the clock line 14 changes to alogic high voltage. Whereas, in the circuit of FIG. 5, the gate drive oftransistor 40 was approximately Vdd−Vtn, the gate drive of transistor 40in the circuit of FIG. 9 is approximately Vdd. This change improvesprecharge efficiency and the strengthens the drive characteristics ofthe circuit.

FIG. 10 shows a NAND gate 80 with reduced charge-sharing effect. In thiscircuit 80, a diode-connected NMOS transistor 82 is added across theinput transistor 60 and the control circuit in FIG. 5 is used. When theclock line 14 is high, node A, between the two input transistors 58, 60,is charged to Vdd−Vtn. This prevents the other input transistor 58 fromsharing charge with the output node 16, thereby preventing a smallvoltage loss on the output node 16. Without transistor 82, when input 76is high and input 78 is low, transistor 58 is on and transistor 60 isoff. If node A is initially at approximately zero volts, output chargeis shared with the parasitic capacitance of transistor 58. Withtransistor 82, node is forced to Vdd−Vtn, reducing the amount of chargetransfer from the output node 16 to the parasitic capacitance at node A.

FIG. 11 shows an INVERTER with reduced charge-pump effect. Thecharge-pump effect occurs because of the parasitic capacitances 43, 45shown in FIG. 5. Parasitic capacitance 43 tends to cause the gate oftransistor 40, after a large number of evaluation phases in which theoutput node was not discharged, to rise toward the high voltage of theclock line 14, in FIG. 5. Also, the charging of the output node duringthe precharge phase, tends to cause the gate of transistor 40 to rise.To counteract the effects of these parasitic capacitances, a stack ofn-channel diode-connected transistors 92, 94, 96 is connected betweenthe gate of transistor 40 and the clock line 14. The number n ofn-channel diode-connected transistors 92, 94, 96 in the stack varies,depending on the magnitude of the positive supply voltage and thethreshold value of the transistors. A stack of n transistors gives avoltage between the clock line and the gate of transistor 40 of aboutn×Vtn, neglecting the body effect for these devices. The drain of then-channel transistor 92 at the top of the stack is connected to the gateof transistor 40 and the source of n-channel transistor 96 at the bottomof the stack is connected to the clock line 14. This transistor stackcontrols the voltage at the gate of transistor 40 at a level thatassures that transistor 40 turns on when the clock line is a logic high.

FIG. 12 shows how an embodiment 38, 54, 56, 70, 80, 90 of the presentinvention interfaces with conventional logic gates. The output node ofthe logic circuit 38, 54, 56, 70, 80, 90 of the present invention isconnected to the input of a traditional inverter circuit 100. With thefull voltage swing operation of the logic circuit of the presentinvention, interfacing with a traditional inverter is improved, becausetime during which the NMOS and PMOS transistors are both on is veryreduced.

FIG. 13 shows a clock circuit block diagram 176 that provides a clocksignal on node X2 to the logic circuitry of the present invention. Theoutput node of the logic circuitry is X1 180. The clock circuit 176includes energy storage circuitry 162 that oscillates at a frequencygoverned by a reference clock ref_clk 174, initialization circuitry 164that starts the oscillations of the energy storage circuit 162, controlcircuitry 160 that maintains the frequency of the oscillations of theenergy storage circuit and an adapter circuitry 166 that periodicallyprovides energy to the energy storage circuit 162 to make up fordissipative losses in the circuitry. Energy storage circuitry 162connects to the voltage return rail 188 via connection 186 and adaptivecircuitry 166 connects to the positive voltage rail 184 via connection182.

FIG. 14 shows an embodiment of the clock circuit block diagram. Theinitialization circuitry 264 connects to the energy storage circuitry262 to initialize oscillations in the energy storage circuitry 262. Thecontrol circuitry 260, which includes a phase detector 256 and a tuningcircuit 258, connects to the output node X2 of the energy storagecircuitry 262 and to a reference clock 274 to control the frequency ofthe oscillations in the energy storage circuitry 262. The adaptivecircuitry 266 also connects to the output X2 of the energy storagecircuitry 262 along with the effective circuit model of the logiccircuitry 268. The effective circuit model includes the discharge path,the precharge path and the control circuitry and any enhancementsthereto such as transistors 72, 74 of FIG. 9, transistor 82 of FIG. 10,or transistors 92, 94 and 96.

In the energy storage circuitry 262, there are two capacitors Co′ 252 aand C1 252 b, where C1 is much smaller than Co′, The junction betweenthe two provides a point of control for the initialization circuitry264.

The initialization circuitry 264 includes an inverter circuit 254 thatis connected to the output of the energy storage circuitry 262 and thejunction of the C1 252 b and Co′ 252 a capacitances. A reset line 202controls whether the inverter 254 has a high-impedance output or a lowimpedance output, which is the inversion of the input. When the resetline 202 is active, the inverter 254 is in the low impedance outputstate, which causes the energy storage circuit 262 to oscillate. Whenthe reset line 202 is deactivated, the inverter 254 changes to ahigh-impedance output and the resonant circuit continues to oscillate onits own with a frequency that is controlled by C1, Co′, Ceff and theoutput, Cx, of the tuning circuit.

As mentioned above, the control circuitry 260 includes a phase detector256 and a tuning circuit 258 that together cause the frequency of theenergy storage circuitry oscillations to be equal to the reference clock274. Phase detector 256 receives the reference clock 274 and the outputX2 of the energy storage circuitry 262, compares the two to control thetuning circuit 258 that modifies the frequency of the energy storagecircuitry 262 to be the same as frequency of the reference clock 274.

Adaptive circuitry 266 is also connected to the output X2 of the energystorage circuitry 262 to replenish energy that is dissipated in thelogic circuitry 268, modeled as an effective resistance Reff andeffective capacitance Ceff.

In operation, the energy storage circuitry 262 begins oscillating at itnatural resonant frequency after the deactivation of the reset line 202.The natural resonant frequency is related inversely to the square rootof the product of L and the value of (Co′∥ C1∥Ceff), where ‘x∥y’ isdefined as the quantity xy/(x+y). If C1′ is much smaller than the othercapacitances, then it is the capacitance that influences the naturalresonant frequency the most (because (Co′∥ C1∥Ceff) is approximatelyequal to C1′). Once started, the energy storage circuitry is then lockedto the reference clock input by the phase detector 256 and tuningcircuit 258. The phase detector 256 detects a phase difference betweenthe energy storage circuitry frequency and the reference clock andconverts this difference into a signal Z that controls the tuningcircuit 258. The tuning circuit 258 then alters the oscillationfrequency of the energy storage circuitry 262 by adding eitherinductance or capacitance into the energy storage circuitry 262 so as todrive the phase difference towards zero. If the amplitude of theoscillations of the energy storage circuit begin to diminish inamplitude, then adaptive circuitry 266 is activated to provide asynchronous energy boost to the oscillations, thereby restoring theamplitude.

Although the present invention has been described in considerable detailwith reference to certain preferred versions thereof, other versions arepossible. Therefore, the spirit and scope of the appended claims shouldnot be limited to the description of the preferred versions containedherein.

What is claimed is:
 1. A logic circuit for operating with a periodicinput, comprising: first and second transistors, each having a gate, anda source and drain with a channel therebetween, the gates of the firstand second transistors for receiving logic inputs, the first and secondtransistors being coupled between a periodic input node and an outputnode and configured to perform a logic function on the logic inputs; athird transistor having a gate, and a source and drain with a channeltherebetween, the channel coupled between the periodic input node andthe output node; and a pair of complementary diode-connectedtransistors, each having a source and a drain and a channel definedtherebetween, the sources of the transistors being connected to theoutput node and the drains being connected to the gate of the thirdtransistor.
 2. A logic circuit as recited in claim 1, wherein the logicfunction as an ‘AND’ function; and wherein the channels of the first andsecond transistors are connected in series, each gate of the first andsecond transistors being connected to one of the logic inputs of the‘AND’ function.
 3. A logic circuit as recited in claim 1, wherein thelogic function is a ‘OR’ function; and wherein the channels of the firstand second transistors are connected in parallel, each gate of the firstand second transistors being connected to one of the logic inputs of the‘OR’ function.
 4. A logic circuit for operating with a periodic input,comprising: a first transistor, having a gate, and a source and drainwith a channel therebetween, the gate of the first for receiving a logicinput, the first transistor being coupled between a periodic input nodeand an output node and configured to perform an inversion logic functionon the logic input; a second transistor having a gate, and a source anddrain with a channel therebetween, the channel coupled between theperiodic input node and the output node; and a pair of complementarydiode-connected transistors, each having a source and a drain and achannel defined therebetween, the sources of the transistors beingconnected to the output node and the drains being connected to the gateof the second transistor.
 5. A logic circuit for operating with aperiodic input, comprising: first and second transistors, each having agate, and a source and drain with a channel therebetween, the gates ofthe first and second transistors for receiving logic inputs, the firstand second transistors being coupled between a periodic input node andan output node and configured to perform a logic function on the logicinputs; a third transistor having a gate, and a source and drain with achannel therebetween, the channel coupled between the periodic inputnode and the output node; fourth and fifth transistors, each having agate, and a source and drain with a channel therebetween, the gates ofthe fourth and fifth transistors being connected, respectively, to thegates of the first and second transistors, the channels of the fourthand fifth transistors being connected in series, the series connectedchannels being connected between the gate of the third transistor andthe periodic input node; and a diode-connected transistor, having asource and a drain and a channel defined therebetween, the source of thetransistor being connected to the output node and the drain beingconnected to the gate of the third transistor.
 6. A logic circuit foroperating with a periodic input, comprising: first and secondtransistors, each having a gate, and a source and drain with a channeltherebetween, the gates of the first and second transistors forreceiving logic inputs, the channels of the first and second transistorsbeing joined at a common node to connect the channels in series so as toperform a logic ‘AND’ function on the logic inputs, the series connectedchannels being coupled between a periodic input node and an output node;a third transistor having a gate, and a source and drain with a channeltherebetween, the channel coupled between the periodic input node andthe output node; a fourth transistor configured as a diode-connectedtransistor having a source connected to the common node and a drainconnected to the periodic inpuit node; and a pair of complementarydiode-connected transistors, each having a source and a drain and achannel defined therebetween, the sources of the transistors beingconnected to the output node and the drains being connected to the gateof the third transistor.
 7. A logic circuit for operating with aperiodic input, comprising: a first transistor, having a gate, and asource and drain with a channel therebetween, the gate of the first forreceiving a logic input, the first transistor being coupled between aperiodic input node and an output node and configured to perform aninversion logic function on the logic input; a second transistor havinga gate, and a source drain with a channel therebetween, the channelcoupled between the periodic input node and the output node third,fourth, and fifth transistors, each having a gate, and a source anddrain with a channel therebetween and each configured as adiode-connected transistor, the channels of each of the third, fourth,and fifth transistors connected so as to form a series, theseries-connected channels being connected between the gate of the secondtransistor and the periodic input node; and a pair of complementarydiode-connected transistors, each having a source and a drain and achannel defined therebetween, the sources of the transistors beingconnected to the output node and the drains being connected to the gateof the second transistor.